EPR Microwave Cavity for Small Magnet Airgaps

ABSTRACT

A microwave resonator for an EPR probe head has a metal cavity body ( 1 ) supporting an electromagnetic microwave resonance mode. The metal cavity body ( 1 ) has an opening for inserting a sample tube ( 2 ) to a center position of the resonator. The center of the opening and the center position of the resonator define an x-axis. The cavity body also has an opening for transmitting microwave radiation into the resonator. Two dielectric elements ( 4   a   , 4   b ) are located symmetrically to the E-field nodal plane containing the x-axis and a z-axis perpendicular to the x-axis. Each dielectric element is geometrically formed and positioned such that it provides an equal overlap with a local maximum of the microwave electric field energy. The microwave resonant cavity has a thin planar shape and the resonator is loaded with two dielectric elements, placed symmetrically relative to the central EPR sample.

This application claims Paris convention priority from EP 15 159 643.4,filed Mar. 18, 2015, the entire disclosure of which is herebyincorporated by reference.

BACKGROUND OF THE INVENTION

The present invention relates to a microwave resonator for an EPR(=“electron paramagnetic resonance”) probe head comprising: a metalcavity body supporting an electromagnetic microwave resonance mode, themicrowave mode having an even number of local maxima of microwaveelectric field energy, at least one opening for inserting a sample tubeto a center position of the resonator, the center of the opening and thecenter position of the resonator defining an x-axis, at least oneopening for transmitting microwave radiation into the resonator, atleast two identical dielectric elements located symmetrically to theplane known as “E-field nodal plane” which contains the x-axis and az-axis perpendicular to the x-axis.

A device of this type is known from U.S. Pat. No. 3,757,204.

In the EPR method it is often desirable or even necessary to performmeasurements at variable temperature conditions on a sample. Theapparatus to irradiate an unknown paramagnetic sample with a microwavefield is called EPR probe head. For easiness of achieving variabletemperature conditions the probe head is usually placed inside of acryostat which is coaxial to the EPR sample insertion mechanism. Thecryostat itself is placed either between the poles of a split-coilmagnet or inside the bore of a solenoid magnet.

For EPR experiments at X-band (8-12 GHz) or higher frequencies the sizeof magnet gap or solenoid bore becomes an important factor in theownership cost of the EPR system. Such a size constraint also directlyaffects the design and performance of EPR probe heads. For example, atX-band or lower frequencies the standard air-filled EPR probe heads donot fit inside usual cryostats. It is necessary to use coaxialtransmission lines instead of waveguides for microwave transmissionwhile for the microwave resonator, as part of the probe head, thissituation has been mitigated in so far by building loop-gap resonators(see e.g. DE 33 00 767 A1 for Split-Ring and BLGR solutions for FlexLine probe heads) or cylindrical shaped dielectric loaded resonantcavities (see e.g. DE 41 25 655 A1 or DE 41 25 653 A1 for Sapphirecylindrical TE011 mode solution for Flex Line probe heads).

In electron-nuclear dual spin resonance experiments, like ENDOR orEPR-DNP, it is often needed to simultaneously optimize the efficiency ofmicrowave and RF field application over the sample volume. Fulfillingthe constraint of optimal EPR and respectively NMR functionalitiesdirectly affects the design and performance of the apparatus.

Another application, the EPRI (EPR Imaging) method, requires thepresence of a multiple sets of coils to create a magnetic gradient atthe unknown sample inside the EPR microwave cavity. The fixture forthese coils should be as mechanically decoupled as possible from thesensitive parts of EPR microwave cavity. This is highly difficult toaccomplish due to space constraints if the cavity has circular symmetry.

It is particularly interesting to observe the influence of experimentalconditions, in particular the temperature, on the microwave concept forEPR probe heads.

For high-sensitivity EPR applications at room temperature conditions thestate-of-the-art EPR probe heads include flat shaped, air-filledmicrowave cavities (see e.g. DE 33 00 767 A1, DE 41 25 655 A1, DE 41 25653 A1, U.S. Pat. No. 3,931,569-A for rectangular TE102, cylindricalTM110 and Reentrant mode probe heads).

For variable temperature experimental conditions, the state-of-the-artEPR probe heads are built around either via loop-gap or dielectricloaded resonating cavities, especially at L, S, C and X-bands in orderto decrease the size of the resonating cavity.

The three versions of flat resonator geometries cited abovetraditionally used at room temperature are missing here. Instead one canfind solutions based on dielectric loaded resonators or loop-gaps havingcircular symmetry along sample length direction. Indeed, such a choicefor resonating mode symmetry is particularly suited to optimize the EPRside of the microwave problem, the filling factor parameter beingconsidered in so far the most important. Attempts to use a coaxial stackof two or more dielectric elements for cavity loading have also beenconsidered but proved to be more difficult than helpful. Even more, foran increasingly larger number of modern EPR applications, the microwavecavity geometries using a single element for dielectric loading alsopresent serious challenges in obtaining a suitable trade-off betweenperformance and usage stability.

It is an object of the invention to achieve performance and qualityenhancements of EPR, EPR-ENDOR/DNP and EPRI variable temperature probeheads. This is realized by flat geometry resonators based on dielectricloaded microwave rectangular TE012 or cylindrical TM110 resonant modeswith dielectric elements having a thickness comparable to the outerdiameter of EPR sample tubes. A full disclosure of the conceptual designfor this new microwave cavity for EPR purposes at variable temperatureconditions or for narrow magnet gaps is the focus of the presentinvention.

U.S. Pat. No. 3,122,703 describes a cooled microwave resonator for EPR.A notched Dewar is used to cool an air-filled rectangular TE102 orcylindrical TM110 resonator.

U.S. Pat. No. 3,931,569 shows in FIGS. 2 and 5 (see present FIGS. 8A and8B, respectively) standard air-filled rectangular TE102 and cylindricalTM110 resonators for EPR.

U.S. Pat. No. 3,757,204 describes different configurations of microwaveresonators employing dielectric material for improving RF fielduniformity along the sample. Especially FIG. 8C (taken from FIG. 4 ofU.S. Pat. No. 3,757,204) depicts a microwave resonator with twodielectric plates extending to either side of the sample.

As the purpose of U.S. Pat. No. 3,757,204 is to homogenize theelectromagnetic RF field in the sample, the dielectric plates arelocated close to the sample as shown in present FIG. 8C. As indicated inpresent FIG. 8D (taken from FIG. 1 of the document U.S. Pat. No.3,757,204) the electric field E of the resonant mode has two maxima leftand right to the center of the sample. To achieve its claimed functions,the dielectric plates in FIG. 8C must not extend into the regions withmaximum of electric field but must increase their extensions in theperipheral regions having less electric field. As claimed, for suchpurposes a first requirement is an overall concave geometry for theinserts. Even more, a second implicit requirement is to maintain thehomogenization of the RF field when a general sample with variousdielectric properties is in the resonator. Whereas in the verticaldirection the dielectric inserts have the same size as the sample andthe resonator, along the shortest side of the resonator they are longercompared to the sample but shorter compared to the resonator length.

However, it is known that higher filling factors in EPR resonatorsrequire a trade-off in the Q-factor of the cavity, which linearlydetermines the EPR signal intensity from the sample. It is also knownthat limiting the sample volume requires a linear trade-off in the EPRsignal intensity. These two trade-offs may cancel the advantages broughtin by the claimed increase of the filling factor and a trade-off in theapplication range for this technical solution occurs. In yet anotherparticular aspect, considering the class of high-sensitivitylow-background EPR probe heads at X-band, usage of this approach in U.S.Pat. No. 3,757,204 does not provide sufficient reduction of resonatorsize to allow to be used in cryostats with standard 2″ access bore,whereas any attempt to decrease the resonator size via dielectricloading using known low-background dielectrics will decrease or cancelthe positive effect expected from the above claimed assumptions.

The present invention describes a way to substantially overcome one ormore disadvantages and trade-offs of the above discussed existingmethods.

One major object of the present invention is to propose a highsensitivity EPR resonator, with low background signals, that achieves asmall size, compatible with narrow gap (<2 cm) magnets or cryostats.

Another object of the present invention is to propose an EPR resonatorwith high efficiency of static or low frequency field irradiation of anEPR sample.

SUMMARY OF THE INVENTION

According to the present invention, these objectives are achieved bymodifying the device discussed above in that each dielectric element isgeometrically formed and positioned such that it provides an equaloverlap with a local maximum of the microwave electric field energy.

In the present invention the materials used for dielectric loading mayexhibit low dielectric constant, for example Teflon, Rexolite and Quartzwhich are all of special interest for use in EPR because of theirexcellent microwave properties and lack of intrinsic EPR signals.

In another aspect the technical solution for obtaining an optimizedgeometry of EPR resonator, compatible with narrow gap magnets orcryostats, consists in a geometry that allows stacks of low frequencyfield coils (modulation, fast sweep, gradient or ENDOR) with planargeometries, protruding or not into the EPR resonator. The optimizedgeometry is considered to allow high efficiency of microwave and RFirradiation at the EPR sample, leading to high sensitivity EPRmeasurements, while minimizing the thermal, microwave and mechanicalnegative effects due to the increased proximity between these coilstacks and the EPR resonator.

In preferred embodiments of the present invention, each of thedielectric elements is elongated along an axis parallel to the x-axis.By this means the symmetry of the microwave mode is conserved and thefilling factor is optimized.

In a further embodiment of the invention, the ratio of the thickness ofthe dielectric elements to the dimension of the opening for insertingthe sample tube, both in direction of the z-axis of the resonator, is inthe range 0.5 to 1.5. Within this range the filling factor can beoptimized and the thickness of the resonator can be minimized.

In another embodiment of the invention, the overlapping is such that atleast 50% of the microwave electric energy is confined within thedielectric elements. An overlap of at least 50% helps minimizing thesize of the resonator and maintains the microwave mode after insertionof an arbitrary sample.

In still another embodiment of the invention, the resonator has a flatstructure having a smallest internal extension along the z-axis equal tothe thickness of the opening for inserting the sample tube or of thedielectric elements, whichever is greater. The flat structure allowsplacements of various field coils external to the resonator.

In a further embodiment of the invention, the dielectric elements areadjustable in a way to change the resonance frequency of the cavitybody. The resonator can thereby be adapted to various experimentalconditions.

In another class of embodiments of the invention, the microwave cavityof the resonator operates in dielectric loaded rectangular TE102 orcylindrical TM110 resonance modes and the dielectric elements are placedparallel to the x-axis centered to the points of microwave E-fieldmaxima. Use of the specified modes allows a simple design of theresonator and the dielectric elements.

In a first variant of this class of embodiments, the resonator is ofcylindrical shape. This shape is optimized for cylindrical resonatormodes.

In a second variant of this class of embodiments, the resonator isbox-shaped. This shape is optimized for rectangular resonator modes.

A further class of embodiments of the invention is characterized by atleast one set of coils for creating a low frequency magnetic fieldtraversing the cavity body and a sample tube, the coils being located atleast partly inside the resonator and the connection to the outside ofthe cavity body being realized by openings in the side walls of thecavity body which are perpendicular to the z-axis. By this means theapplied low frequency magnetic field is coupled very efficiently to theEPR sample as it is very close to the sample. In this aspect the turnsof the coil are not fully contained in the resonator thereby minimizingtheir influence on the microwave mode in the resonator.

In a first variant of this class of embodiments, the windings of thecoil are completely outside the cavity body. By this means the influenceon the microwave mode in the resonator is eliminated.

In an alternative variant, the sections of the windings of the coilinside the cavity body have a general orientation parallel to thex-axis. By orientation parallel to the x-axis the influence in themicrowave mode is minimized.

This class of embodiments can be further improved in that the resonatorcomprises metallized side plates having openings for providing access tofield coils inside the resonator. Thereby the efficiency of the fieldcoils is further optimized.

The present invention comprises also an EPR probe head with a microwaveresonator as described above and a housing for holding the resonatorlocated in a static magnetic field along the z-axis.

A preferred embodiment of such EPR probe head according to the presentinvention is characterized in that the probe head is placed inside acryostat with the cavity body of the resonator being spaced from theinnermost walls of the cryostat, and that the space between the cryostatand the resonator is equipped with modules containing stacks of lowfrequency planar coils for creating main magnetic field modulationand/or gradient fields and/or for fields for ENDOR or NMR excitation anddetection.

These, as well as other objects and advantages of this invention can bebetter understood and appreciated through careful study of the followingdetailed description of presently preferred exemplary embodiments ofthis invention in conjunction with the accompanying drawing.

In order to make the aforesaid and other features and advantages of thepresent invention more apparent to those skilled in the art, preferredembodiments of the present invention will be described in detail belowby referring to the accompanying drawings, wherein identical numeralsrepresent the same parts.

BRIEF DESCRIPTION OF THE DRAWING

FIG. 1 shows a 3-dimensional sectional view of an embodiment of theinvention;

FIG. 2 shows a schematic cross-sectional view through a horizontalmiddle plane of an EPR probe head comprising a microwave resonatoraccording to the invention being located inside a cryostat;

FIG. 3A shows a schematic cross-sectional view through a vertical middleplane of a first embodiment of the EPR microwave resonator according tothe invention applied to a rectangular TE102 resonance mode;

FIG. 3B shows a schematic cross-sectional view through a vertical middleplane of second embodiment of the EPR microwave resonator according tothe invention applied to a cylindrical TM110 mode;

FIG. 4A shows the embodiment of FIG. 3A in greater detail;

FIG. 4B shows the embodiment of FIG. 3B in greater detail;

FIG. 5 shows several schematic 3-dimensional views of some possibleshapes of dielectric elements used in embodiments of the EPR resonatoraccording to the invention;

FIG. 6-1 A-F illustrates the effect of increasing the dielectric loading(overlapping) in the regions of high E-field (energy) in six plots.

FIG. 6-2 A-F shows the percent amount of electric energy localizedwithin the entire volume of the dielectric inserts versus the totalelectric energy of the mode enclosed in the cavity.

FIG. 7 shows a schematic representation for the embodiment of the fieldcoils partially protruding into the EPR resonator from the side platesparallel to a sample.

FIG. 8A-D is a selection of a relevant diagrams from prior art discussedearlier.

DESCRIPTION OF THE PREFERRED EMBODIMENT

A simplified example of the novel EPR experimental setup according tothe present invention is shown in FIG. 1. The dielectric 4 a,b loadedflat microwave cavity 1, is shown accompanied by a variable temperaturecryostat 5, magnet poles 21 of an external magnet creating a main staticmagnetic field and a modulation coil 7 responsible for creating themodulation magnetic field traversing the EPR cavity and the paramagneticsample 2 in an EPR experiment. The sample mostly consists of a tubeholding a substance to be measured. When describing features of theresonator related to the position of the sample it is understood thisequivalent to the space provided for accommodation of the sample. Forclarity all other details concerning mechanical or microwave standardimplementations were suppressed (various supports, coaxial microwavetransmission line and microwave coupling structure necessary to excitethe microwave resonance which is relevant for EPR use).

It is an object of this invention to disclose a microwave resonantcavity of thin planar shape for an EPR probe head. The resonator isloaded with two dielectric elements, of identical shape and physicalproperties, placed symmetrically relative to the central EPR sample.When included in a probe head the resonator is also contained by themirror symmetry plane between the main magnet poles.

FIG. 2 represents this construction by a cross section in transversalplane relative to the EPR sample access axis. The height of cut plane isset through the middle of EPR active region.

The EPR microwave cavity is composed of a metal cavity body 1 and twolateral side plates 3A and 3B. These three elements are electricallyconnected continuously throughout their line of contact to eliminate theleakage of microwave field. The cavity body 1 has other openings such asthe access bores 12 for the EPR sample 2 and the access bore 13 for astandard microwave coupling structure via iris aperture or coaxialantenna feed (not shown in this drawing).

Magnet poles (not shown in this drawing) create the uniform staticmagnetic field oriented along an axis, which normally coincides with thez-axis (6) of the resonator. The unknown paramagnetic sample 2 to bemeasured by EPR method is contained in a cylindrical fused quartz tubeand oriented perpendicular to axes 6 and 8, the latter (8) defining ay-axis being usually called the front-back axis of the magnet. Thecenter of the opening 12 for inserting a sample and the center positionof the resonator defines an x-axis (11). The electric field has a nodalplane (“E-Field nodal plane”) which contains the x-axis and a z-axisperpendicular to the x-axis. In the nodal plane the E field amplitudedisappears.

According to the present invention, the EPR microwave cavity containstwo identical dielectric inserts 4A and 4B placed symmetrically to theworking position of an EPR sample 2, their position on axis 8 beingapproximately the location of maximum microwave electric field componentalong axis 6 and therefore the local maximum of the electric fieldenergy. Their exact position is determined by the microwave mode usedand by the details of EPR cavity 1 inclusive by shape and dielectricproperties of the inserts 4A and 4B and the EPR sample 2 and may beadjustable for resonance frequency tuning reasons. The details of theshape for dielectric inserts 4A and 4B will be discussed later below.

The side plates 3A and 3B, which are perpendicular to axis 6, arerealized using standard microwave materials and structures for EPRapplications to allow low frequency magnetic fields (from DC to someMHz) to penetrate the entire cavity and the unknown EPR sample 2. Forexample, the modulation field could be created outside the resonator bymodulation coils 7A and 7B. The metallic side plates 3A and 3B aresufficiently thin and could be locally opened, avoiding leakage of highfrequency microwave, but increasing the penetration of low frequencyfields created by respective coils placed externally to this cavityalong axis 6 and symmetrically with respect to axis 8. Alternatively,such local openings of side plates can be used for the insertion of lowfrequency field coils (ex. Fast-Sweep or ENDOR coils) inside the EPRcavity (see FIG. 7). In both cases however the condition for lowmicrowave leakage must be fulfilled. It is new to CW-EPR to provideaccess for field coils from the side plates.

FIG. 2 reflects several critical aspects pertinent to the presentinvention regarding the size of the claimed EPR cavity and its placementinside the variable temperature cryostat 5.

Firstly, it is easily observed that the available space to accommodatelow frequency planar coils is sufficient, i.e. space between the cavityside plates 3A and 3B and the geometrical limits imposed by cryostat 5,has been increased dramatically in comparison to currentstate-of-the-art solutions for EPR cavities of circular symmetry.

A second important aspect is the possibility to place the low frequencycoils to the minimal possible distance to sample 2, defined only by itsouter diameter and not by the volume of EPR cavity.

A third advantage of the claimed EPR cavity refers to the shape andconstruction of dielectric inserts 4A and 4B. Their geometry can beadapted, from case to case, in order to obtain the desired shape of themicrowave magnetic field distribution across the sample, according tothe sample geometry and properties, according to the desiredfunctionality of the microwave cavity parameters (for example cavityshape and volume, resonant frequency on the desired mode of operation,quality and filling factors) or presence of other various metallic ordielectric inserts in the cavity (for example a pair of Endor coils).

This conceptual flexibility to match the microwave cavity to a given EPRapplication represents a major advantage of this present invention. FIG.5 shows a variety of other geometries of dielectric inserts that may beused in the claimed EPR cavity for optimization to the givenapplications like CW, Pulsed, EPR-Imaging.

The resonance frequency for either rectangular TE102 or cylindricalTM110 mode without dielectric loading is mostly independent of thecavity thickness along the z-axis. In the case of dielectric loading forthe same two resonant modes the result is largely different. Differentvalues for the ratio between thicknesses of the dielectric elements andof the cavity will affect the TE102 and TM110 modes resonance frequency.

The use of higher permittivity dielectric materials for 4A and 4B willenhance the change of resonance frequency with the thickness ratio. Itis advantageous that the thickness of dielectric elements 4A and 4Balong the z-axis varies in a range from 0.5× to 1.5× relative to theopening 12 for inserting a sample tube 2 in order to obtain optimalsolutions for a large range of EPR applications (e.g. high sensitivity,Pulsed EPR, etc.; general aspects can be found in “Electron SpinResonance” by Charles P. Poole 1997, 978-0-486-69444-3 (ISBN)). If therelative size of the dielectric elements is not in the optimum range thequality of the system decreases (e.g. sensitivity, B1).

Also, according to present invention, the total thickness of the cavityalong the z-axis should be nearly equal to the thickness of thedielectric elements 4A and 4B, or to the opening 12 for inserting asample tube 2, whichever is greater.

FIG. 3A and FIG. 3B show the microwave relevant elements of the twopreferred embodiments of this invention, depicting a rectangular TE102mode and a cylindrical TM110 mode.

The two figures show the H-field (flux lines) patterns 9 in a planedefined by the plane of y-axis 8 and the x-axis 11. In both figures allelements are labeled identically, having the same functionalities, whilekeeping also the same meanings as in FIG. 2. Since only the magneticfield lines penetrating the sample are affecting a resonance absorptionsignal from the paramagnetic spins in the sample, the presence ofelectrical field at the sample should be normally avoided. The EPRresonators and their choice of resonant mode fulfill this condition, andthe regions of strong electric field are placed away from the sample bymeans of suitable choice of the dielectric elements shape and position.For rectangular TE102 and cylindrical TM110 modes the local maxima ofthe E-field (including the effect of dielectric loading) are locatedapproximately in the middle between sample center and respective wallsof the resonator along axis 8.

In FIG. 4A and FIG. 4B, the same cross section plane as in FIG. 3A andFIG. 3B, respectively, is used to show in more detail the constructionelements, including dielectric inserts supports 10.

The supports 10 are adapted to the longitudinal and transversal geometryof the dielectric inserts 4A and 4B as well as to the cavity body 1 andto side plates 3A and 3B. Therefore, since all these are variables inboth microwave concept and technological implementation, the use ofrectangular shapes must not be considered as limiting within the meaningof the present invention.

The same non-limiting considerations must be acknowledged for theassumed rectangular geometry for the dielectric inserts, this choicebeing only relevant for the description of the preferred embodiment ofthe present invention. In a real apparatus their transversal crosssection could be square, rectangular, cylindrical, tubular, ellipsoidalor even a combination of these (see several options in FIG. 5), as wellas it should be clear that the cross-sections of elements 4A and 4B mustnot be constant along their length in order to work for an apparatusdescribed in this disclosure. The dielectric elements 4A and 4B shouldonly be required to have a central region that protrudes significantlyinto the high E-field microwave regions, as exemplified in the plots ofFIG. 6-1D-F such that preferably more than 50% of electric field energyis confined in the central region of these elements.

FIG. 6-1 shows the effect of increasing the dielectric loading(overlapping) in the regions of high E-field. The figures show theperiphery of a rectangular resonator containing two dielectric elements(depicted transparent for clarity) shaped differently in the respectiveplots. Lines indicate the iso-lines of equal electric field strength ofa rectangular TE102 mode with lowest values at the walls of theresonator. At the same time the E field iso-lines represent the B1 fieldlines of the microwave. As the electric field energy is proportional tothe square of the electric field these diagrams describe the change ofelectric field energy as well.

In the first 3 plots FIG. 6-1 A-C (12.8 GHz, 12.1 GHz and 11.6 GHz) theeffect induced by “concave dielectric elements” similar to Hyde U.S.Pat. No. 3,757,204 is shown. The E-field distribution is seen to be moreelongated in the direction parallel to sample 2, improving the spatialhomogeneity of the B1-field, as required in Hyde U.S. Pat. No.3,757,204.

In the last 3 plots FIG. 6-1 D-F (11.0 GHz, 10.5 GHz and 9.74 GHz) thetwo dielectric elements overlap the regions of E-field maximum resultingin a “focused” distribution of electrical energy inside the resonator.As can be seen the homogeneity of the B1 field at sample region betweenthe dielectric elements has decreased. Furthermore, increased dimensionof the dielectric elements, i.e. increased dielectric loading, resultsin a slight decrease of the frequency of resonance. According to theinvention an overlap of the central dielectric regions with thepositions of maximum E-field, will not cease to function if theelectrical energy included in these regions are above 50% of the entiremicrowave energy in the cavity, therefore sustaining the same resonancemodes for any choice of shape and dielectric strength. This is shown inFIG. 6-2.

FIG. 6-2 A-F shows the percent amount of electric energy localizedwithin the entire volume of the dielectric inserts versus the totalelectric energy of the mode enclosed in the cavity for the sameconfigurations as in FIG. 6-1 A-F. To enhance the visualization of theeffect in the previous paragraph, these plots represent the distributionof electrical “energy density” in the x-y-plane. The size of circlesrepresents the amount of this “energy density”. The filled/open displayof circles represents the values of “energy density” of those circleswhich passed/missed 50% of the full range of “energy density”.

FIG. 7 shows the microwave resonator 1 in a cut parallel to a planedefined by the x-axis (11) and the z-axis (6). The sample tube 2 isinserted into the resonator and extends to the left side of the figure.Side plates 3 a and 3 b cover the sides of the resonator. Coils (7 c, 7d) used for creating a low frequency magnetic field are traversing thecavity body through holes in the side plates (3 a, 3 b). The windings ofthe coils are located at least partially inside the resonator. Sectionsof windings in the resonator have a general orientation along the x-axis(11).

For clear definition of parameters, the thickness T of the resonatorshall be the distance between the two parallel planes bounding thecavity which are perpendicular to the E field nodal plane and parallelto the x-axis. The height H of the resonator is considered to bemeasured along the x-axis and the width W is the maximal distancebetween the cavity walls along the direction perpendicular to the x-axisand the z-axis.

Preferred dimensions of the microwave resonator at X-band (8-12 GHz) areW×H×T 22 mm×(20+/−2) mm×5 mm.

Preferably the dielectric elements are made of Quartz and haverectangular dimensions of e.g. W×H×T 4.5 mm×(17+/−2) mm×4.5 mm.Separation of the dielectric elements (center to center) is 11 mm.

While only certain features of the invention have been illustrated anddescribed herein, many modifications and changes will occur to thoseskilled in the art. It is, therefore, to be understood that the appendedclaims are intended to cover all such modifications and changes as fallwithin the true spirit of the invention.

We claim:
 1. A microwave resonator for an EPR (=“electron paramagneticresonance”) probe head, the resonator comprising: a metal cavity bodystructured for supporting an electromagnetic microwave resonance mode,said microwave resonance mode having an even number of local maxima ofmicrowave electric field energy, said metal cavity body having at leastone first opening for inserting a sample tube to a center position ofthe resonator, wherein a center of said first opening and a centerposition of the resonator define an x-axis, said metal cavity body alsohaving at least one second opening for transmitting microwave radiationinto the resonator; and at least two substantially identical dielectricelements disposed symmetrically with respect to an E-field nodal plane,said E-field nodal plane containing said x-axis and a z-axis which isperpendicular to said x-axis, wherein each dielectric element isgeometrically formed and positioned to provide an equal overlap with alocal maximum of said microwave electric field energy.
 2. The resonatorof claim 1, wherein each of said dielectric elements is elongated alongan axis parallel to said x-axis.
 3. The resonator of claim 1, wherein aratio of a thickness of said dielectric elements to a dimension of saidfirst opening, both in a direction of said z-axis of the resonator, isin a range of 0.5 to 1.5.
 4. The resonator of claim 1, wherein saidequal overlap is such that at least 50% of said microwave electric fieldenergy is confined within said dielectric elements.
 5. The resonator ofclaim 1, wherein the resonator has a flat structure having a smallestinternal extension along said z-axis substantially equal to a thicknessof said first opening or of said dielectric elements, whichever isgreater.
 6. The resonator of claim 1, wherein said dielectric elementsare adjustable in order to change a resonance frequency of said cavitybody.
 7. The resonator of claim 1, wherein the resonator is ofcylindrical shape.
 8. The resonator of claim 1, wherein the resonator isbox-shaped.
 9. The resonator of claim 1, further comprising at least oneset of coils for creating a low frequency magnetic field traversing saidcavity body and the sample tube, said coils being located at leastpartly inside the resonator, said coils having a connection to anoutside of the cavity body via openings in the side walls of said cavitybody which are perpendicular to said z-axis.
 10. The resonator of claim9, wherein windings of said coils are completely outside said cavitybody.
 11. The resonator of claim 9, wherein a section of windings ofsaid coils inside said cavity body has a general orientation parallel tosaid x-axis.
 12. The resonator of claim 9, wherein the resonatorcomprises metallized side plates having openings for providing access tosaid coils inside the resonator.
 13. The resonator of claim 1, whereinsaid cavity body of the resonator operates in dielectric loadedrectangular TE102 or cylindrical TM110 resonance modes, and saiddielectric elements are placed parallel to said x-axis centered topoints of microwave E-field maxima.
 14. An EPR probe head comprising themicrowave resonator of claim 1, further comprising a housing for holdingthe resonator located in a static magnetic field along said z-axis. 15.The EPR probe head of claim 14, further comprising a cryostat withinwhich said probe head is placed, wherein said cavity body of theresonator is spaced from innermost walls of said cryostat, and a spacebetween said cryostat and the resonator is equipped with modulescontaining stacks of low frequency planar coils for creating mainmagnetic field modulation, gradient fields, and/or for fields for ENDORor NMR excitation and detection.